A comparative performance study of four-pole induction motors and synchronous reluctance motors in variable speed drives

Design aspects of the Transversally Laminated Anisotropic (TLA) Synchronous Reluctance Motor (SynRM) are studied and the machine performance analysis compared to the Induction Motor (IM) is done. The SynRM rotor structure is designed and manufactured for a30 kW, four-pole, three-phase squirrel cage induction motor stator. Both the IMand SynRM were supplied by a sensorless Direct Torque Controlled (DTC) variablespeed drive. Attention is also paid to the estimation of the power range where the SynRM may compete successfully with a same size induction motor. A technicalloss reduction comparison between the IM and SynRM in variable speed drives is done. The Finite Element Method (FEM) is used to analyse the number, location and width of flux barriers used in a multiple segment rotor. It is sought for a high saliency ratio and a high torque of the motor. It is given a comparison between different FEM calculations to analyse SynRM performance. The possibility to take into account the effect of iron losses with FEM is studied. Comparison between the calculated and measured values shows that the design methods are reliable. A new application of the IEEE 112 measurement method is developed and used especially for determination of stray load losses in laboratory measurements. The study shows that, with some special measures, the efficiency of the TLA SynRM is equivalent to that of a high efficiency IM. The power factor of the SynRM at rated load is smaller than that of the IM. However, at lower partial load this difference decreases and this, probably, brings that the SynRM gets a better power factor in comparison with the IM. The big rotor inductance ratio of the SynRM allows a good estimating of the rotor position. This appears to be very advantageous for the designing of the rotor position sensor-less motor drive. In using the FEM designed multi-layer transversally laminated rotor with damper windings it is possible to design a directly network driven motor without degrading the motorefficiency or power factor compared to the performance of the IM.

Salient Pole Synchronous Machine Modelling in an Industrial Direct Torque Controlled Drive Application

Synchronous motors are used mainly in large drives, for example in ship propulsion systems and in steel factories' rolling mills because of their high efficiency, high overload capacity and good performance in the field weakening range. This, however, requires an extremely good torque control system. A fast torque response and a torque accuracy are basic requirements for such a drive. For large power, high dynamic performance drives the commonly known principle of field oriented vector control has been used solely hitherto, but nowadays it is not the only way to implement such a drive. A new control method Direct Torque Control (DTC) has also emerged. The performance of such a high quality torque control as DTC in dynamically demanding industrial applications is mainly based on the accurate estimate of the various flux linkages' space vectors. Nowadays industrial motor control systems are real time applications with restricted calculation capacity. At the same time the control system requires a simple, fast calculable and reasonably accurate motor model. In this work a method to handle these problems in a Direct Torque Controlled (DTC) salient pole synchronous motor drive is proposed. A motor model which combines the induction law based "voltage model" and motor inductance parameters based "current model" is presented. The voltage model operates as a main model and is calculated at a very fast sampling rate (for example 40 kHz). The stator flux linkage calculated via integration from the stator voltages is corrected using the stator flux linkage computed from the current model. The current model acts as a supervisor that prevents only the motor stator flux linkage from drifting erroneous during longer time intervals. At very low speeds the role of the current model is emphasised but, nevertheless, the voltage model always stays the main model. At higher speeds the function of the current model correction is to act as a stabiliser of the control system. The current model contains a set of inductance parameters which must be known. The validation of the current model in steady state is not self evident. It depends on the accuracy of the saturated value of the inductances. Parameter measurement of the motor model where the supply inverter is used as a measurement signal generator is presented. This so called identification run can be performed prior to delivery or during drive commissioning. A derivation method for the inductance models used for the representation of the saturation effects is proposed. The performance of the electrically excited synchronous motor supplied with the DTC inverter is proven with experimental results. It is shown that it is possible to obtain a good static accuracy of the DTC's torque controller for an electrically excited synchronous motor. The dynamic response is fast and a new operation point is achieved without oscillation. The operation is stable throughout the speed range. The modelling of the magnetising inductance saturation is essential and cross saturation has to be considered as well. The effect of cross saturation is very significant. A DTC inverter can be used as a measuring equipment and the parameters needed for the motor model can be defined by the inverter itself. The main advantage is that the parameters defined are measured in similar magnetic operation conditions and no disagreement between the parameters will exist. The inductance models generated are adequate to meet the requirements of dynamically demanding drives.

Design and analysis of a transversal-flux switched-reluctance-linear-machine pole-pair

The Switched Reluctance technology is probably best suited for industrial low-speed or zerospeed applications where the power can be small but the torque or the force in linear movement cases might be relatively high. Because of its simple structure the SR-motor is an interesting alternative for low power applications where pneumatic or hydraulic linear drives are to be avoided. This study analyses the basic parts of an LSR-motor which are the two mover poles and one stator pole and which form the “basic pole pair” in linear-movement transversal-flux switchedreluctance motors. The static properties of the basic pole pair are modelled and the basic design rules are derived. The models developed are validated with experiments. A one-sided one-polepair transversal-flux switched-reluctance-linear-motor prototype is demonstrated and its static properties are measured. The modelling of the static properties is performed with FEM-calculations. Two-dimensional models are accurate enough to model the static key features for the basic dimensioning of LSRmotors. Three-dimensional models must be used in order to get the most accurate calculation results of the static traction force production. The developed dimensioning and modelling methods, which could be systematically validated by laboratory measurements, are the most significant contributions of this thesis.

Design of salient pole PM synchronous machines for a vehicle traction application – Analysis and

This doctoral thesis presents a study on the development of a liquid-cooled frame salient pole permanent-magnet-exited traction machine for a four-wheel-driven electric car. The emphasis of the thesis is put on a radial flux machine design in order to achieve a light-weight machine structure for traction applications. The design features combine electromagnetic and thermal design methods, because traction machine operation does not have a strict operating point. Arbitrary load cycles and the flexible supply require special attention in the design process. It is shown that accurate modelling of the machine magnetic state is essential for high-performance operation. The saturation effect related to the cross-saturation has to be taken carefully into account in order to achieve the desired operation. Two prototype machines have been designed and built for testing: one totally enclosed machine with a special magnet module pole arrangement and another through-ventilated machine with a more traditional embedded magnet structure. Both structures are built with magnetically salient structures in order to increase the torque production capability with the reluctance torque component. Both machine structures show potential for traction usage. However, the traditional embedded magnet design turns out to be mechanically the more secure one of these two machine options.

A new & accurate map of the North Pole with all the countries hitherto discovered situated near or adjacent to it as well as some others more remote. Drawn from the latest and best authorities and regulated by astronom.l observat.ns by Eman. Bowen.

0-meridiaani: Lontoo. - Koordinaattiasteikko: N90°-55°[50°].

Sähkökoneen staattorikäämityksen kehittäminen

Tämä insinöörityö tehtiin ABB:n Pitäjänmäen konetehtaalle Tahtikoneet-tulosyksikölle. Työssä tutkittiin mahdollisuuksia valmistaa murtovakovyyhtejä kestomagneettituuligeneraattoreihin, joissa vakoluku on alle yhden. Työ tehtiin tutustumalla aluksi Pitäjänmäen konetehtaan käytössä oleviin vyyhden valmistus- ja käämintämenetelmiin. Lisäksi tutkittiin erilaisia mahdollisia murtovakovyyhden valmistusmenetelmiä, joista lupaavimpia myös kokeiltiin. Saatujen kokemusten pohjalta valittiin vyyhden valmistusmenetelmä, jonka mukaan valmistettiin koe-erä. Koe-erälle suoritettiin mittauksia, joilla varmistettiin niiden sähköinen kestävyys Työn tuloksena valitulla valmistusmenetelmällä valmistettiin vyyhdet prototyyppi tuuligeneraattorin.

Fractional slot permanent magnet synchronous motors for low speed applications

This study compares different rotor structures of permanent magnet motors with fractional slot windings. The surface mounted magnet and the embedded magnet rotor structures are studied. This thesis analyses the characteristics of a concentrated two-layer winding, each coil of which is wound around one tooth and which has a number of slots per pole and per phase less than one (q < 1). Compared to the integer slot winding, the fractional winding (q < 1) has shorter end windings and this, thereby, makes space as well as manufacturing cost saving possible. Several possible ways of winding a fractional slot machine with slots per pole and per phase lessthan one are examined. The winding factor and the winding harmonic components are calculated. The benefits attainable from a machine with concentrated windingsare considered. Rotor structures with surface magnets, radially embedded magnets and embedded magnets in V-position are discussed. The finite element method isused to solve the main values of the motors. The waveform of the induced electro motive force, the no-load and rated load torque ripple as well as the dynamic behavior of the current driven and voltage driven motor are solved. The results obtained from different finite element analyses are given. A simple analytic method to calculate fractional slot machines is introduced and the values are compared to the values obtained with the finite element analysis. Several different fractional slot machines are first designed by using the simple analytical methodand then computed by using the finite element method. All the motors are of thesame 225-frame size, and have an approximately same amount of magnet material, a same rated torque demand and a 400 - 420 rpm speed. An analysis of the computation results gives new information on the character of fractional slot machines.A fractional slot prototype machine with number 0.4 for the slots per pole and per phase, 45 kW output power and 420 rpm speed is constructed to verify the calculations. The measurement and the finite element method results are found to beequal.

Permanent magnet synchronous motor for industrial inverter applications - analysis and design

During the latest few years the need for new motor types has grown, since both high efficiency and an accurate dynamic performance are demanded in industrial applications. For this reason, new effective control systems such as direct torque control (DTC) have been developed. Permanent magnet synchronous motors (PMSM) are well suitable for new adjustable speed AC inverter drives, because their efficiency and power factor are not depending on the pole pair number and speed to the same extent as it is the case in induction motors. Therefore, an induction motor (IM) with a mechanical gearbox can often be replaced with a direct PM motor drive. Space as well as costs will be saved, because the efficiency increases and the cost of maintenance decreases as well. This thesis deals with design criterion, analytical calculation and analysis of the permanent magnet synchronous motor for both sinusoidal air-gap flux density and rectangular air-gapflux density. It is examined how the air-gap flux, flux densities, inductances and torque can be estimated analytically for salient pole and non-salient pole motors. It has been sought by means of analytical calculations for the ultimate construction for machines rotating at relative low 300 rpm to 600 rpm speeds, which are suitable speeds e.g. in Pulp&Paper industry. The calculations are verified by using Finite Element calculations and by measuring of prototype motor. The prototype motor is a 45 kW, 600 rpm PMSM with buried V-magnets, which is a very appropriate construction for high torque motors with a high performance. With the purposebuilt prototype machine it is possible not only to verify the analytical calculations but also to show whether the 600 rpm PMSM can replace the 1500 rpm IM with a gear. It can also be tested if the outer dimensions of the PMSM may be the same as for the IM and if the PMSM in this case can produce a 2.5 fold torque, in consequence of which it may be possible to achieve the same power. The thesis also considers the question how to design a permanent magnet synchronous motor for relatively low speed applications that require a high motor torqueand efficiency as well as bearable costs of permanent magnet materials. It is shown how a selection of different parameters affects the motor properties. Key words: Permanent magnet synchronous motor, PMSM, surface magnets, buried magnets

Torque vibration model of axial-flux surface-mounted permanent magnet synchronous machine

In order that the radius and thus ununiform structure of the teeth and otherelectrical and magnetic parts of the machine may be taken into consideration the calculation of an axial flux permanent magnet machine is, conventionally, doneby means of 3D FEM-methods. This calculation procedure, however, requires a lotof time and computer recourses. This study proves that also analytical methods can be applied to perform the calculation successfully. The procedure of the analytical calculation can be summarized into following steps: first the magnet is divided into slices, which makes the calculation for each section individually, and then the parts are submitted to calculation of the final results. It is obvious that using this method can save a lot of designing and calculating time. Thecalculation program is designed to model the magnetic and electrical circuits of surface mounted axial flux permanent magnet synchronous machines in such a way, that it takes into account possible magnetic saturation of the iron parts. Theresult of the calculation is the torque of the motor including the vibrations. The motor geometry and the materials and either the torque or pole angle are defined and the motor can be fed with an arbitrary shape and amplitude of three-phase currents. There are no limits for the size and number of the pole pairs nor for many other factors. The calculation steps and the number of different sections of the magnet are selectable, but the calculation time is strongly depending on this. The results are compared to the measurements of real prototypes. The permanent magnet creates part of the flux in the magnetic circuit. The form and amplitude of the flux density in the air-gap depends on the geometry and material of the magnetic circuit, on the length of the air-gap and remanence flux density of the magnet. Slotting is taken into account by using the Carter factor in the slot opening area. The calculation is simple and fast if the shape of the magnetis a square and has no skew in relation to the stator slots. With a more complicated magnet shape the calculation has to be done in several sections. It is clear that according to the increasing number of sections also the result will become more accurate. In a radial flux motor all sections of the magnets create force with a same radius. In the case of an axial flux motor, each radial section creates force with a different radius and the torque is the sum of these. The magnetic circuit of the motor, consisting of the stator iron, rotor iron, air-gap, magnet and the slot, is modelled with a reluctance net, which considers the saturation of the iron. This means, that several iterations, in which the permeability is updated, has to be done in order to get final results. The motor torque is calculated using the instantaneous linkage flux and stator currents. Flux linkage is called the part of the flux that is created by the permanent magnets and the stator currents passing through the coils in stator teeth. The angle between this flux and the phase currents define the torque created by the magnetic circuit. Due to the winding structure of the stator and in order to limit the leakage flux the slot openings of the stator are normally not made of ferromagnetic material even though, in some cases, semimagnetic slot wedges are used. In the slot opening faces the flux enters the iron almost normally (tangentially with respect to the rotor flux) creating tangential forces in the rotor. This phenomenon iscalled cogging. The flux in the slot opening area on the different sides of theopening and in the different slot openings is not equal and so these forces do not compensate each other. In the calculation it is assumed that the flux entering the left side of the opening is the component left from the geometrical centre of the slot. This torque component together with the torque component calculated using the Lorenz force make the total torque of the motor. It is easy to assume that when all the magnet edges, where the derivative component of the magnet flux density is at its highest, enter the slot openings at the same time, this will have as a result a considerable cogging torque. To reduce the cogging torquethe magnet edges can be shaped so that they are not parallel to the stator slots, which is the common way to solve the problem. In doing so, the edge may be spread along the whole slot pitch and thus also the high derivative component willbe spread to occur equally along the rotation. Besides forming the magnets theymay also be placed somewhat asymmetric on the rotor surface. The asymmetric distribution can be made in many different ways. All the magnets may have a different deflection of the symmetrical centre point or they can be for example shiftedin pairs. There are some factors that limit the deflection. The first is that the magnets cannot overlap. The magnet shape and the relative width compared to the pole define the deflection in this case. The other factor is that a shifting of the poles limits the maximum torque of the motor. If the edges of adjacent magnets are very close to each other the leakage flux from one pole to the other increases reducing thus the air-gap magnetization. The asymmetric model needs some assumptions and simplifications in order to limit the size of the model and calculation time. The reluctance net is made for symmetric distribution. If the magnets are distributed asymmetrically the flux in the different pole pairs will not be exactly the same. Therefore, the assumption that the flux flows from the edges of the model to the next pole pairs, in the calculation model from one edgeto the other, is not correct. If it were wished for that this fact should be considered in multi-pole pair machines, this would mean that all the poles, in other words the whole machine, should be modelled in reluctance net. The error resulting from this wrong assumption is, nevertheless, irrelevant.

Design of axial-flux permanent-magnet low-speed machines and performance comparison between radial-flux and axial-flux machines

This thesis presents an alternative approach to the analytical design of surface-mounted axialflux permanent-magnet machines. Emphasis has been placed on the design of axial-flux machines with a one-rotor-two-stators configuration. The design model developed in this study incorporates facilities to include both the electromagnetic design and thermal design of the machine as well as to take into consideration the complexity of the permanent-magnet shapes, which is a typical requirement for the design of high-performance permanent-magnet motors. A prototype machine with rated 5 kW output power at 300 min-1 rotation speed has been designed and constructed for the purposesof ascertaining the results obtained from the analytical design model. A comparative study of low-speed axial-flux and low-speed radial-flux permanent-magnet machines is presented. The comparative study concentrates on 55 kW machines with rotation speeds 150 min-1, 300 min-1 and 600 min-1 and is based on calculated designs. A novel comparison method is introduced. The method takes into account the mechanical constraints of the machine and enables comparison of the designed machines, with respect to the volume, efficiency and cost aspects of each machine. It is shown that an axial-flux permanent-magnet machine with one-rotor-two-stators configuration has generally a weaker efficiency than a radial-flux permanent-magnet machine if for all designs the same electric loading, air-gap flux density and current density have been applied. On the other hand, axial-flux machines are usually smaller in volume, especially when compared to radial-flux machines for which the length ratio (axial length of stator stack vs. air-gap diameter)is below 0.5. The comparison results show also that radial-flux machines with alow number of pole pairs, p < 4, outperform the corresponding axial-flux machines.

Sähkönjakeluverkon komponenttien pitoajat

Suomessa sähkönjakeluverkkoyhtiöt toimivat verkkovastuualueillaan yksinoikeudella. Verkkovastuualuiden ominaispiirteet voivat olla hyvin erilaiset. Energiamarkkinavirasto valvoo sähkömarkkinalainsäädännön noudattamista jakeluverkkotoiminnassa. Jakeluverkonhaltijat on velvoitettu Energiamarkkinaviraston valvontamallin kautta määrittämään tiettyjen rajoitusten mukaisesti verkkokomponenteillensa sopivimmat teknistaloudelliset pitoajat. Nämä pitoajat vaikuttavat varsinkin verkkoyhtiön tuottomahdollisuuksiin ja asiakkaiden siirtohintoihin. Lisäksi huomioon on otettava jaettavan sähkön laatu, verkon käyttövarmuus sekä vaikutukset ympäristöön ja turvallisuuteen. Pitoaikojen matemaattinen mallintaminen on usein monimutkaista. Teknistaloudellinen pitoaika valitaankin monesti kokemuksen ja harkinnan perusteella. Tärkeimmät reunaehdot jakeluverkkokomponenttien teknistaloudellisten pitoaikojen valinnalle muodostavat verkkovastuualueen sähkönkulutuksen kasvun sekä infrastruktuurin muutoksen nopeudet. Hitaan muutoksen alueilla verkkokomponenttien teknistaloudelliset pitoajat lähenevät teknisiä pitoaikoja, joihin vaikuttavat voimakkaasti verkkovastuualueen maantieteelliset ja ilmastolliset ominaispiirteet. Yhtiöittäin vaihtelevat verkon rakennus- ja ylläpitomenetelmät tulee myös huomioida. Tässä diplomityössä keskitytään pääosin sähkönjakeluverkon komponenttien teknistaloudelliseen pitoaikaan verkon ja verkkovastuualueen ominaispiirteiden kautta. Aluksi määritellään jakeluverkon pitoaika usealla eri tavalla, sekä selvitetään pitoajan merkitystä nykytilanteessa. Lisäksi työn alkuosassa esitellään Energiamarkkinaviraston vuoden 2005 alusta käyttöönotettu jakeluverkkotoiminnan hinnoittelun kohtuullisuuden valvontamalli ja käydään läpi teknistaloudellisen pitoajan merkitys siinä. Sen jälkeen tarkastellaan jakeluverkkokomponenttien ja niiden osien tekniseen pitoaikaan vaikuttavia tekijöitä. Erityisesti puupylväisiin ja niihin liittyviin ajankohtaisiin asioihin kiinnitetään huomiota, koska puupylväät määräävät monesti koko ilmajohtorakenteen uusimisajankohdan. Lisäksi suolakyllästeiselle puupylväälle esitetään yleinen rappeutumismalli ja jakelumuuntajan rappeutumistapahtumaa tutkitaan. Lopuksi tarkastellaan Graninge Kainuu Oy:tä jakeluverkonhaltijana sekä määritetään sen verkkovastuualueelle ominaisia komponenttien teknisiä ja teknistaloudellisia pitoaikoja haastattelujen, tuoreimpien lähteiden, tutkimustulosten, vertailun ja harkinnan avulla.

Elinkaarikustannusten ja toimitusvarmuuden analysointi sähkönjakelun saneerausmenetelmille

Tässä työssä tutkitaan haja-asutusalueiden sähkönjakeluverkkojen kehittämistä. Kehityskohteiksi on valittu viisi tekniikkaa, 1000 V-järjestelmä, keskijännitejohtojen siirtäminen teiden varsille, PAS -johtojen käyttö, maakaapelointi sekä pylväskatkaisijan käyttö. Teoreettisen tarkastelun tavoitteena on määrittää reunaehdot tarkasteltavien tekniikoiden kannattavuudelle. Aiemmin keskijänniteverkko on rakennettu lähes poikkeuksetta avojohtona. Viime vuosien myrskyt sekä lumikuormat ovat häirinneet sähkönjakelua ja nostaneet painetta jakeluvarmuuden kasvattamiseksi. Tutkimuksessa haja-asutusalueiden sähkönjakeluverkon kehittämiseen etsitään teknillisesti sekä taloudellisesti kannattavia ratkaisumalleja. Kehittämisen tavoitteena on parantaa kuluttajien sähkön laatua ja toimitusvarmuutta. Tutkimuksessa käsitellään tarkasteltavia tekniikoita esimerkkikohteiden avulla, jotka on valittu Itä-Suomelle tyypillisiltä jakelualueilta. Kohteissa taloudellista kannattavuutta tutkitaan vertaamalla perinteistä saneeraamista tarkastelussa oleviin korvaaviin menetelmiin. Korvaavilla ratkaisuilla toimitusvarmuus paranee, mutta kannattavuus riippuu siirrettävästä tehosta, asiakasryhmien jakaumasta sekä saavutettavasta vikataajuuden muutoksesta.

DTC-induktiomoottorikäytön soveltaminen keskitaajuusalueelle

Työssä tarkastellaan olemassa olevan suoraa vääntömomentin säätöä käyttävän taajuudenmuuttajan soveltamista keskitaajuusalueella toimiviin induktiomoottorikäyttöihin. Keskinopeusalueen sovellusten pyörimisnopeudet ovat tyypillisesti 6000…30000rpm. Tällöin invertterin lähtötaajuuden on nelinapaista moottoria ohjattaessa ulotuttava 1000Hz:iin. ABB:n ACS600 taajuudenmuuttajan nykyinen syöttötaajuus ulottuu noin 400Hz:iin ja sen keskimääräinen kytkentätaajuus on luokkaa 3kHz. Taajuudenmuuttajan keskimääräistä kytkentätaajuutta ei haluta tästä merkittävästi nostaa, koska tällöin pääteasteen mitoitusta ja rakennetta on muutettava. Tarkastelussa keskitytään täten jännitemodulointiin, joka määrittelee invertterin lähtöjännitteen käyrämuodon ja pääteasteen tehokytkimien kytkentätaajuuden. Työssä esitetään suoran käämivuon säädön periaatetta soveltava 30-kulmainen modulointimenetelmä (30-modulointi), jolla moottorin syöttövirrasta voidaan eliminoida 5. ja 7. yliharmoninen komponentti. Yliharmonisten komponenttien eliminointi mahdollistaa passiivisilla komponenteilla toteutetun alipäästösuodattimen asentamisen invertterin lähtöön, jolloin moottorissa tapahtuvat tehohäviöt saadaan pieniksi. 30-moduloinnin ohjaukseen ja säätöön esitetään menetelmät, jotka mahdollistavat sen toteuttamisen nykyiseen taajuudenmuuttajaan ohjelmallisesti ilman suuria laitteistomuutoksia. 30-moduloinnin ominaisuuksia tarkastellaan analyyttisin menetelmin ja sen toimintaa testataan esitettyjen teorioiden perusteella simuloimalla. 30-moduloinnin ohjelmallinen implementointi nykyiseen ACS600:een mahdollistaa periaatteessa noin 600Hz:n syöttötaajuuden saavuttamisen. Tällöin invertterin keskimääräinen kytkentätaajuus voidaan säätää koko pyörimisnopeusalueella alle 4kHz:n tasolle.